Primary line constants
The primary line constants are parameters that describe the characteristics of copper (or other conductive material) transmission lines in terms of the physical electrical properties of the line. The primary line constants are only relevant to copper lines and are to be contrasted with the secondary line constants, which can be derived from them, and are more generally applicable. The secondary line constants can be used, for instance, to compare the characteristics of a waveguide to a copper line, whereas the primary constants have no meaning for a waveguide.
Contents
The constants
There are four primary line constants, but in some circumstances some of them are small enough to be ignored and the analysis can be simplified. These four, and their symbols and units are as follows;
| Name | Symbol | Units | Unit symbol |
|---|---|---|---|
| loop resistance | R | ohms per metre | Ω/m |
| loop inductance | L | henries per metre | H/m |
| insulator capacitance | C | farads per metre | F/m |
| insulator conductance | G | siemens per metre | S/m |
R and L are elements in series with the line (because they are properties of the conductor) and C and G are elements shunting the line (because they are properties of the dielectric material between the conductors). G represents leakage current through the dielectric and in most cables is very small. The word loop is used to emphasise that the resistance and inductance of both conductors must be taken into account. For instance, if a line consists of two identical wires that have a resistance of 25 mΩ/m each, the loop resistance is double that, 50 mΩ/m. Because the values of the constants are quite small, it is common for manufacturers to quote them per kilometre rather than per metre; in the English speaking world per mile can also be used.[1][2]
The word constant can be misleading as there is some variation with frequency. In particular, R is heavily influenced by the skin effect. Furthermore, while G has virtually no effect at audio frequency, it can cause noticeable losses at high frequency with many of the dielectric materials used in cables due to a high loss tangent. Avoiding the losses caused by G is the reason many cables designed for use at UHF are air-insulated or foam-insulated (which makes them virtually air-insulated).[3] The actual meaning of constant in this context is that the parameter is constant with distance. That is the line is assumed to be homogenous lengthwise. This condition is true for the vast majority of transmission lines in use today.[4]
Typical values for some common cables
| Designation | Cable form | Application | R | L[5] | G | C | Z0[5] |
|---|---|---|---|---|---|---|---|
| Ω/km | μH/km | nS/km | nF/km | Ω | |||
| CAT5[6] | Twisted pair | Data transmission | 176 | 490 | <2 | 49 | 100 |
| CAT5e[7] | Twisted pair | Data transmission | 176 | <2 | 100 | ||
| CW1308[8] | Twisted pair | Telephony | 98 | <20 | |||
| RG59[9] | Coaxial | Video | 36 | 430 | 69 | 75 | |
| RG59[10] | Coaxial (foam dielectric) |
Video | 20.4 | 303 | 54 | 75 | |
| RG58[11][12] | Coaxial | Radio frequency | 48 | 253 | <0.01 | 101 | 50 |
| Low loss[13] | Coaxial (Foam dielectric) |
Radio frequency transmitter feed |
2.86 | 188 | 75 | 50 | |
| DIN VDE 0816[14] | Star quad | Telephony (trunk lines) |
31.8 | <0.1 | 35 |
Circuit representation
The line constants cannot be simply represented as lumped elements in a circuit; they must be described as distributed elements. For instance "pieces" of the capacitance are in between "pieces" of the resistance. However many pieces the R and C are broken into, it can always be argued they should be broken apart further to properly represent the circuit, and after each division the number of meshes in the circuit is increased. To give a true representation of the circuit, the elements must be made infinitesimally small so that each element is distributed along the line as shown in figure 1. The infinitesimal elements in an infinitesimal distance <math>\scriptstyle dx</math> are given by;[15]
- <math>dL=\lim_{\delta x \to 0}(L\delta x)=Ldx</math>
- <math>dR=\lim_{\delta x \to 0}(R\delta x)=Rdx</math>
- <math>dC=\lim_{\delta x \to 0}(C\delta x)=Cdx</math>
- <math>dG=\lim_{\delta x \to 0}(G\delta x)=Gdx</math>
It is convenient for the purposes of analysis to roll up these elements into general series impedance, Z, and shunt admittance, Y elements such that;
- <math>dZ=(R+i \omega L)dx=Zdx\, ,</math> and,
- <math>dY=(G+i \omega C)dx=Ydx\, .</math>
Analysis of this network (figure 2) will yield the secondary line constants: the propagation constant, <math>\scriptstyle \gamma</math>, (whose real and imaginary parts are the attenuation constant, <math>\scriptstyle \alpha</math>, and phase change constant, <math>\scriptstyle \beta</math>, respectively) and the characteristic impedance, <math>\scriptstyle Z_0</math>, which also, in general, will have real, <math>\scriptstyle R_0</math>, and imaginary, <math>\scriptstyle X_0</math>, parts, making a total of four secondary constants to be derived from the four primary constants. The term constant is even more misleading for the secondary constants as they all usually vary quite strongly with frequency, even if the frequency dependence of the primary constants is ignored. This is because the reactances in the circuit (<math>\scriptstyle \omega L</math> and <math>\scriptstyle 1/(\omega C)</math>) introduce a dependence on <math>\scriptstyle \omega</math>. It is possible to choose specific values of the primary constants that result in <math>\scriptstyle \alpha</math> and <math>\scriptstyle Z_0</math> being constant (the Heaviside condition) but even in this case there is still <math>\scriptstyle \beta</math> which is directly proportional to <math>\scriptstyle \omega</math>. As with the primary constants, the meaning is that the secondary constants do not vary with distance along the line, not that they are independent of frequency.[16][17][18]
Characteristic impedance
The characteristic impedance of a transmission line, <math>\scriptstyle Z_0</math>, is defined as the impedance looking into an infinitely long line. Such a line will never return a reflection since the incident wave will never reach the end to be reflected. When considering a finite initial length of the line, the remainder of the line can be replaced by <math>\scriptstyle Z_0</math> as its equivalent circuit. This is so because the remainder of the line is still infinitely long. Considering just the first section of the equivalent circuit of the line (this is an L-network consisting of one element each of <math>\scriptstyle dZ</math> and <math>\scriptstyle dY</math>) the remainder can be replaced by <math>\scriptstyle Z_0</math>. This results in the network shown in figure 3, which can be analysed for <math>\scriptstyle Z_0</math> using the usual network analysis theorems,[19][20]
- <math>Z_0 = \delta Z + \frac {Z_0}{1+Z_0 \delta Y}</math>
which re-arranges to,
- <math>{Z_0}^2 - Z_0 \delta Z = \frac {\delta Z}{\delta Y}</math>
Taking limits of both sides
- <math>\lim_{\delta x \to 0}({Z_0}^2 - Z_0 \delta Z) = {Z_0}^2 = \frac {dZ}{dY}</math>
and since the line was assumed to be homogenous lengthwise,
- <math>{Z_0}^2 = \frac {Z}{Y}</math>
Propagation constant
The ratio of the line input voltage to the voltage a distance <math>\scriptstyle \delta x</math> further down the line, that is, after one infinitesimal section, is given by a standard voltage divider calculation. The remainder of the line to the right, as in the characteristic impedance calculation, is replaced with <math>\scriptstyle Z_0</math>,[21][22]
- <math>\frac {V_\mathrm i}{V_{x1}} = \frac{\delta Z+\frac{Z_0 /\delta Y}{Z_0+1/\delta Y}}{\frac{Z_0 /\delta Y}{Z_0+1/\delta Y}}
= 1 + \frac {\delta Z}{Z_0} + \delta Z \delta Y</math>
Each infinitesimal section will multiply the voltage drop by the same factor. After <math>\scriptstyle n</math> sections the voltage ratio will be,
- <math>\frac {V_\mathrm i}{V_{xn}} = \left ( 1 + \frac {\delta Z}{Z_0} + \delta Z \delta Y \right)^n</math>
At a distance <math>\scriptstyle x</math> along the line, the number of sections is <math>\scriptstyle x/\delta x</math> so that,
- <math>\frac {V_\mathrm i}{V_{xn}} = \left ( 1 + \frac {\delta Z}{Z_0} + \delta Z \delta Y \right)^{\frac{x}{\delta x}}</math>
In the limit as <math>\scriptstyle \delta x \to 0</math>,
- <math>\frac {V_\mathrm i}{V_x} = \lim_{\delta x \to 0} \frac {V_\mathrm i}{V_{xn}} = \lim_{\delta x \to 0} \left ( 1 + \frac {\delta Z}{Z_0} + \delta Z \delta Y \right)^{\frac{x}{\delta x}}</math>
The second order term <math>\scriptstyle \delta Z \delta Y </math> will disappear in the limit, so we can write without loss of accuracy,
- <math>\frac {V_\mathrm i}{V_x} = \lim_{\delta x \to 0} \left ( 1 + \frac {\delta Z}{Z_0} \right)^{\frac{x}{\delta x}}</math>
and comparing with the mathematical identity,
- <math>e^x \equiv \lim_{p \to \infin} (1+1/p)^{px}</math>
yields,
- <math>V_\mathrm i = V_x e^{\frac{Z}{Z_0}x}</math>
From the definition of propagation constant,
- <math>V_\mathrm i = V_x e^{\gamma x}\,\!</math>
Hence,
- <math>\gamma = \frac{Z}{Z_0} = \sqrt {ZY}</math>
Special cases
An ideal transmission line will have no loss, which implies that the resistive elements are zero. It also results in a purely real (resistive) characteristic impedance. The ideal line cannot be realised in practice, but it is a useful approximation in many circumstances. This is especially true, for instance, when short pieces of line are being used as circuit components such as stubs. A short line has very little loss and this can then be ignored and treated as an ideal line. The secondary constants in these circumstances are;[23]
- <math>\gamma = i \omega \sqrt {LC}</math>
- <math>\alpha = 0\,</math>
- <math>\beta = \omega \sqrt {LC}</math>
- <math>Z_0 = \sqrt \frac{L}{C}</math>
Twisted pair
Typically, twisted pair cable used for audio frequencies or low data rates has line constants dominated by R and C. The dielectric loss is usually negligible at these frequencies and G is close to zero. It is also the case that, at a low enough frequency, <math>\scriptstyle R \gg \omega L</math> which means that L can also be ignored. In those circumstances the secondary constants become,[24]
- <math>\gamma \approx \sqrt {i\omega CR}</math>
- <math>\alpha \approx \sqrt \frac{\omega CR}{2}</math>
- <math>\beta \approx \sqrt \frac{\omega CR}{2}</math>
- <math>Z_0 \approx \sqrt \frac{R}{i\omega C} = \sqrt \frac{R}{2\omega C} - i \sqrt \frac{R}{2\omega C}</math>
The attenuation of this cable type increases with frequency which causes distortion of waveforms. Not so obviously, the variation of <math>\scriptstyle \beta</math> with frequency also causes a distortion of a type called dispersion. To avoid dispersion the requirement is that <math>\scriptstyle \beta</math> is directly proportional to <math>\scriptstyle \omega</math>. However, it is actually proportional to <math>\scriptstyle \sqrt \omega</math> and dispersion results. <math>\scriptstyle Z_0</math> also varies with frequency and is also partly reactive; both these features will be the cause of reflections from a resistive line termination. This is another undesirable effect. The nominal impedance quoted for this type of cable is, in this case, very nominal, being valid at only one spot frequency, usually quoted at 800 Hz or 1 kHz.[25][26]
Co-axial cable
Cable operated at a high enough frequency (VHF radio frequency or high data rates) will meet the conditions <math>\scriptstyle R \ll \omega L</math> and <math>\scriptstyle G \ll \omega C</math>. This must eventually be the case as the frequency is increased for any cable. Under those conditions R and G can both be ignored (except for the purpose of calculating the cable loss) and the secondary constants become;[27]
- <math>\gamma \approx i \omega \sqrt {LC}</math>
- <math>\alpha \approx \frac{LG+RC}{2\sqrt{LC}} = \tfrac{1}{2}\left(Z_0 G + \frac{R}{Z_0}\right) \approx \frac{R}{2Z_0}</math>
- <math>\beta \approx \omega \sqrt {LC}</math>
- <math>Z_0 \approx \sqrt \frac{L}{C}</math>
Loaded line
Loaded lines are lines designed with deliberately increased inductance. This is done by adding iron or some other magnetic metal to the cable or adding coils. The purpose is to ensure that the line meets the Heaviside condition by doing which eliminates attenuation and dispersion distortions and ensures that <math>\scriptstyle Z_0</math> is constant and resistive. The secondary constants are here related to the primary constants by;[28]
- <math>\gamma = \sqrt {RG} + i \omega \sqrt {LC}</math>
- <math>\alpha = \sqrt {RG}</math>
- <math>\beta = \omega \sqrt {LC}</math>
- <math>Z_0 = \sqrt \frac{L}{C} = \sqrt \frac{R}{G}</math>
Notes
Cite error: Invalid <references> tag;
parameter "group" is allowed only.
<references />, or <references group="..." />References
- F.R. Connor, Wave Transmission, Edward Arnold Ltd., 1972 ISBN 0713132787.
- John Bird, Electrical circuit theory and technology, Newnes, 2007 ISBN 075068139X.
- Ian Hickman, Analog electronics, Newnes, 1999 ISBN 0750644168.
- Fred Porges, The design of electrical services for buildings, Taylor & Francis, 1989 ISBN 0419145907.
